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coolset ? - q1 ICE2QR0665G off-line smps quasi-resonant pwm controller with integrated 650v coolmos ? and startup cell in dso-16/12 never stop thinking. power management & supply datasheet,version 2.0, july 4, 2011
edition 2011-07-04 published by ? infineon technologies ag ? 81726 mnchen, germany ? infineon technologies ag 7/4/11. ? all rights reserved. attention please! the information given in this data sheet shall in no event be regarded as a guarantee of conditions or characteristics (?beschaffenheitsgarantie?). with respect to any examples or hints giv en herein, any typical values stated herein and/or any information regarding the application of the device, infineon technologies hereby disclaims any and all warranties and liabilities of any kind, including without limitation warranties of non-infringement of intellectual property rights of any third party. information for further information on technology, delivery terms and conditions and prices pl ease contact your nearest infineon technologies office ( www.infineon.com ). warnings due to technical requirements components may contain dangerous substances. for information on the types in question please contact your near est infineon technologies office. infineon technologies components may only be used in life-support devices or systems with the express written approval of infineon technologies, if a failure of such components can reasonably be expected to cause the failure of that life-support device or system, or to affect the safe ty or effectiveness of that device or system. life support devices or systems are intended to be implanted in the human body, or to support and/or maintain and sustain and/or protect human life. if they fail, it is reasonable to assume that the health of the user or other persons may be endangered. for questions on technology, delivery and prices please contact the infineon technologi es offices in germany or the infineon technologies companies and repres entatives worldwide: see our we bpage at http://www.infineon.com coolmos ? , coolset ? are trademarks of infineon technologies ag. coolset ? - q1 ? ICE2QR0665G ? revision history: july 4, 2011 datasheet previous version: 1.0 page subjects (major changes since last revision)
type package marking v ds r dson 1) 1) typ @ t=25c 230vac 15% 2) 2) calculated maximum input power rating at t a =50c, t i =125c and without copper area as heat sink. 85-265 vac 2) ICE2QR0665G pg-dso-16/12 2qr0665g 650v 0.65 79w 45w coolset ? - q1 ICE2QR0665G version 2.0 3 july 4, 2011 off-line smps quasi-resonant pwm controller with integrated 650v coolmos ? and startup cell in dso-16/12 pg-dso-16/12 description the coolset ? -q1 series (ice2qrxx65) is the first generation of quasi-resonant in tegrated power ics. it is optimized for off-line switch mode power supply applications such as lcd monitor, dvd r/ w, dvd combo, blue-ray dvd, set top box, etc. operating the mosfet switch in quasi-resonant mode, lower emi, higher efficiency and lower voltage stress on secondary diodes are expected for the smps. based on the bicmos technology, the coolset ? -q1 series has a wide operation range (up to 25v) of ic power supply and lower power consumption. it also offers many advantages such as quasi-resona nt operation till very low load which increases the average system efficiency, active burst mode operation which enables an ultra-low power consumption at standby mode with small and controllable output voltage ripple, etc. product highlights ? quasi resonant operation ? active burst mode to reach the lowest standby power requirement <100mw@no load ? digital frequency reduction for better overall system efficiency ? integrated 650v avalanche rugged coolmos ? with startup cell ? pb-free lead platin g; rohs compliant features ? 650v avalanche rugged coolmos ? with built-in startup cell ? quasiresonant operation till very low load ? active burst mode operation for low standby input power (< 0.1w) ? digital frequency reduction with decreasing load for reduced switching loss ? built-in digital soft-start ? foldback point correction and cycle-by-cycle peak current limitation ? maximum on/off time limitation ? auto restart mode for vcc overvoltage and undervoltage protections ? auto restart mode for overload protection ? auto restart mode for overtemperature protection ? latch-off mode for adjustable output overvoltage protection and transformer short-winding protection 85 ~ 265 vac snubber c bus d r1 ~d r4 r cs tl431 optocoupler r b1 r b2 r c1 c c1 c c2 r ovs2 r ovs1 c vcc d vcc d o c o l f c f v o c ps startup cell coolset ? -q1 coolmos ? w p w s w a r vcc c zc r zc2 r zc1 drain zero crossing block power management cycle-by-cycle current limitation active burst mode pwm controller current mode control protections vcc cs control unit zc fb gnd
coolset ? - q1 ICE2QR0665G table of contents page version 2.0 4 july 4, 2011 1 pin configuration and functionality . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 1.1 pin configuration with pg-dso-16/12 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 1.2 package pg-dso-16/12 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 1.3 pin functionality . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 2 representative blockdiagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 3 functional description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 3.1 vcc pre-charging and typical vcc voltage during start-up . . . . . . . . . . . . . . . . 7 3.2 soft-start . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 3.3 normal operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 3.3.1 digital frequency reduction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 3.3.1.1 up/down counter . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8 3.3.1.2 zero crossing (zc counter) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8 3.3.1.3 ringing suppression time . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9 3.3.2 switch off determination . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9 3.4 current limitation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9 3.4.1 foldback point correction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9 3.5 active burst mode operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 3.5.1 entering active burst mode operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 3.5.2 during active burst mode operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 3.5.3 leaving active burst mode operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 3.6 protection functions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11 4 electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 4.1 absolute maximum ratings . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 4.2 operating range . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 4.3 characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 3 4.3.1 supply section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13 4.3.2 internal voltage reference . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13 4.3.3 pwm section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 4.3.4 current sense . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 4.3.5 soft start . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 4.3.6 foldback point correction . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 4.3.7 digital zero crossing . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 4.3.8 active burst mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 4.3.9 protection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16 4.3.10 coolmos ? section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16 5 typical coolmos ? performance characteristic . . . . . . . . . . . . . . . . . . . . . . . . 17 6 input power curve . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19 7 outline dimension . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20
version 2.0 5 july 4, 2011 coolset ? - q1 ICE2QR0665G pin configuration and functionality 1 pin configuration and functionality 1.1 pin configuratio n with pg-dso-16/ 12 pin symbol function 1 zc zero crossing 2 fb feedback 3 n.c. not connected 4 cs current sense 5 drain 650v 1) 1) at t j = 110c coolmos? drain 6 drain 650v 1) coolmos? drain 7 drain 650v 1) coolmos? drain 8 drain 650v 1) coolmos? drain 9 n.c. not connected 10 n.c. not connected 11 vcc controller supply voltage 12 gnd controller ground 1.2 package pg-dso-16/12 10 11 12 9 vcc fb n.c. cs zc n.c. gnd n.c. drain drain 8 7 3 2 1 4 drain drain 5 6 figure 1 pin configuration pg-dso-16/12 (top view) 1.3 pin functionality zc (zero crossing) at this pin, the voltage from the auxiliary winding after a ti me delay circuit is applied. in ternally, this pin is connected to the zero-crossing detector for switch-on determination. additionally, the output overvoltage detection is realized by comparing the voltage vzc with an internal preset threshold. fb (f eedback) normally, an external c apacitor is connected to this pin for a smooth voltage v fb . internally, this pin is connected to the pwm signal generator for switch-off determination (together with the current sensing signal), the digital signal processing for the frequency reduction with decreasing load during normal operation, and the active burst mode controller for entering active burst mode operation determination and burst ratio control during active burst mode operation. additionally , the open-loop / over-load protection is implemented by monitoring the voltage at this pin. cs (cu rrent sense) this pin is connected to the external shunt resistor for the prim ary current sensing an d the internal pwm signal generator for switch-off determination (together with the feedback voltage). moreover, short-winding protection is realised by monitoring the voltage v cs during on-time of the main power switch. drain ( drain of integrated coolmos ? ) drain pin is the connection to the drain of the internal c oolmos ?. vcc (power supply) vcc pin is the positive supply of the ic. the operating range is between v vccoff and v vccovp . gnd (ground ) this is the common ground of the controller.
coolset ? - q1 ICE2QR0665G representative blockdiagram version 2.0 6 july 4, 2011 2 representative blockdiagram 1 g2 1 g7 r sq latched protect r sq autorestart protect protection r fb 1 g3 25k o 2pf d1 & g1 & g5 1 g4 t beb & g6 active burst block fb c8 v fbeb c9 v fbbon c10 v fbboff c3 v zcrs c2 v zcovp delay t zcovp f sb osc active burst mode t count c1 v zcc zc up/down counter zc counter clk comparator soft-start ringing suppression count=7 v ref r s q g8 & g9 startup cell drain cs vcc gate drive g pwm pwm op current mode pwm comparator v pwm q voltage reference undervoltage lockout 18v 10.5 10us internal bias power management coolmos ? t onmax c7 v fbzl c6 v fbzh c5 v fbr1 c4 v fbolp t olp_b regulation current limiting 10k o d1 leading edge blanking t leb 1pf foldback correction delay t cssw c13 v csb c14 v cssw c15 pwm control zero crossing gate driver gnd en c12 v vccovp t offmax otp figure 2 representative block diagram
version 2.0 7 july 4, 2011 coolset ? - q1 ICE2QR0665G functional description 3 functional description 3.1 vcc pre-charging and typical vcc voltage during start-up in ICE2QR0665G, a startup cell is integrated into the coolmos ? . as shown in figure 2, the start cell consists of a high voltage device and a c ontroller, whereby the high voltage device is controlled by the controller. the startup cell provides a pre-charging of the vcc capacitor till vcc voltage reaches the vcc turned-on threshold v vccon and the ic begins to operate. once the mains input voltage is app lied, a rectified voltage shows across the capacitor c bus . the high voltage device provides a current to char ge the vcc capacitor c vcc . before the vcc voltage reaches a certain value, the amplitude of the current through the high voltage device is only determined by its channel resistance and can be as high as several ma. after the vcc voltage is high en ough, the controller controls the high voltage device so that a constant current around 1ma is provided to charge th e vcc capacitor further, until the vcc voltage exceeds the turned-on threshold v vccon . as shown in the time phase i in figure 3 , the vcc voltage increase near linearly and the charging speed is independent of the mains voltage level. v vccon v vcc v vccoff t1 t t2 iiiiii figure 3 vcc voltage at start up the time taking for the vcc pre-charging can then be approxi mately calculated as: [1] where i vcccharge2 is the charging current from the startup cell which is 1.05ma, typically. when the vcc voltage ex c eeds the vcc turned-on threshold v vccon at time t 1 , the startup cell is switched off and the ic begins to operate with soft-start. due to power consumption of the ic and the fact that there is still no energy from the auxiliary winding to charge the vcc capacitor before the output voltage is built up, the vcc voltage drops (phase ii). once the output voltage is high enough, the vcc capacitor receives the ener gy from the auxiliary winding from the time point t 2 onward. the vcc will then reach a constant value depending on output load. 3.2 soft-start as shown in figure 4 , at the time t on , the ic begins to operate with a soft-start. by th is soft-start the switching stresses for the switch, diode and transformer are minimised. the soft-start implemented in ICE2QR0665G is a digital time-based function. the preset soft-start time is 12ms with 4 steps. if not limited by other functions, the peak voltage on cs pin will increase step by step from 0.32v to 1v finally. t on 3691 2 0.32 0.49 0.66 0.83 1.00 vcs_sst (v) time(ms) figure 4 maximum current sense voltage during soft start 3.3 normal operation the pwm controller during normal operation consists of a digital signal processing circuit including an up/down counter, a zero-crossing counter (zc counter) and a comparator, and an analog circuit including a current measurement unit and a compar ator. the switch-on and -off time points are determined by the digital circuit and the analog circuit respectively. the zero-crossing input signal and the value of the up/down counter are needed for the switch-on determination while the feedback signal v fb and the current sensing signal v cs are necessary for the switch- off determination. details a bout the full operation of the pwm controller in normal operation are illustrated in the following paragraphs. 3.3.1 digital frequency reduction as mentioned above, the digi tal si gnal processing circuit consists of an up/down counter, a zc counter and a comparator. these three parts are key to implement digital frequency reduction with decr easing load. in addition, a ringing suppression time controller is implemented to avoid mistriggering by the high frequency oscillation when the output voltage is very low under conditions such as soft start period or output short circuit. fu nctionality of these parts is described in the following. 3.3.1.1 up/down counter the up/down counter stores the number of the zero crossing wher e the main power switch is switched on after demagnetisation of the transfor mer. this value is fixed t 1 v vccon c vcc ? i vccch e2 arg ------------------------------------------ =
coolset ? - q1 ICE2QR0665G functional description version 2.0 8 july 4, 2011 according to the feedback voltage, v fb , which contains information about the output power. indeed, in a typical peak current mode control, a high output power results in a high feedback voltage, and a low output power leads to a low regulation voltage. hence, according to v fb , the value in the up/down counter is changed to vary the power mosfet off- time according to the output power. in the following, the variation of the up/down coun ter value according to the feedback voltage is explained. the feedback voltage v fb is internally co mpared with three threshold voltages v fbzl , v fbzh and v fbr1 , at each clock period of 48ms. the up/down counter counts then upward, keep unchanged or count downw ard, as shown in table 1. table 1 operation of th e up/down counter v fb up/down counter act ion always lower than v fbzl count upwards till 7 once higher than v fbzl , but always lower than v fbzh stop counting, no value changing once higher than v fbzh , but always lower than v fbr1 count downwards till 1 once higher than v fbr1 set up/down counter to 1 in the ICE2QR0665G, the number of zero crossing is limited to 7. therefore, the counter varies between 1 and 7, and any attempt beyond this range is ignored. when v fb exceeds v fbr1 voltage, the up/down counter is reset to 1, in order to allow the system to react rapidly to a sudden load increase. the up/down counter value is also reset to 1 at the start-up time, to ensure an efficient maximum load start up. figure 5 shows some examples on how up/down counter is changed accordi ng to the feedback voltage over time. the use of two different thresholds v fbzl and v fbzh to count upward or downward is to prevent frequency jittering when the feedback voltage is close to the threshold point. however, for a stable operatio n, these two thresholds must not be affected by the foldback current limitation (see section 3.4.1), which limits the v cs voltage. hence, to prevent such situation, the threshold voltages, v fbzl and v fbzh , are changed internally depending on the line voltage levels. 1 case 3 case 2 case 1 up/down counter n n+1 n+2 n+2 n+2 n+2 n+1 n n-1 4 5 6 6 6 6 5 4 3 1 1 2 3 4 4 4 4 3 2 1 7 7 7 7 7 7 6 5 4 t t v fb v fbr1 v fbzh v fbzl clock t=48ms 1 figure 5 up/down counter operation 3.3.1.2 zero crossing (zc counter) in the system, the voltage from the auxiliary winding is ap plied to the zero-crossing pin through a rc network, which provides a time delay to the voltage from the auxiliary winding. internally, this pin is connected to a clamping network, a zero-crossing detect or, an output overvoltage detector and a ringing supp ression time controller. during on-state of the powe r swi tch a negative voltage applies to the zc pin. through the internal clamping network, the voltage at the pin is clamped to certain level. the zc counter has a minimum value of 0 and maximum val ue of 7. after the internal mosfet is turned off, every time when the falling voltage ramp of on zc pin crosses the 100mv threshold, a zero crossing is detected and zc counter will increase by 1. it is reset every time after the driver output is changed to high. the voltage v zc is also used for the output overvoltage detection. once the voltage at this pin is higher than the threshold v zcovp during off-time of the main switch, the ic is latched off after a fixed blanking time. to achieve the switch-on at vo ltage vall ey, the voltage from the auxiliary winding is fed to a time delay ne twork (the rc network consists of d zc , r zc1 , r zc2 and c zc as shown in typical application circuit) before it is applied to the zero-crossing detector through the zc pin. th e needed time delay to the main oscillation signal d t should be approximately one fourth of the oscillation period (by transformer primary inductance and drain-source capacitance) minus the propagation delay from the detected zero-crossing to the switch-on of the main switch t delay , theoretically: [2] ' t t osc 4 ------------ t delay ?=
coolset ? - q1 ICE2QR0665G functional description version 2.0 9 july 4, 2011 this time delay should be matched by adjusting the time constant of the rc network which is calculated as: [3] 3.3.1.3 ringing suppression time after mosfet is turned off, there will be some oscillation on v ds , which will also appear on the voltage on zc pin. to avoid mistriggering by such oscillations to turn on the mosfet, a ringing suppression timer is implemented. this suppresion time is depended on the voltage v zc . if the voltage v zc is lower than the threshold v zcrs , a longer preset time is applied. howe ver, if the voltage v zc is higher than the threshold, a shorter time is set. 3.3.1.4 switch on determination after the gate drive goes to low, it can not be changed to high duri ng ring suppression time. after ring suppression time, the gate driv e can be turned on when the zc counter value is higher or equal to up/down counter value. however, it is also possible that the oscillation between prim ary inductor and drain-sour ce capacitor damps very fast and ic can not detect enough zero crossings and zc counter value will not be high enough to tu rn on the gate drive. in this case, a maximum off time is implemented. after gate drive has been remained off for the period of t offmax , the gate drive will be turned on again regard less of the coun ter values and v zc . this function can effectively prevent the switching frequency from going lower than 20khz. otherwise it will cause audible noise, during start up. 3.3.2 switch off determination in the converter system, the primary current is sensed by an external s hunt resistor, which is connected between low-side terminal of the main power switch and the common ground. the sensed voltage across the shunt resistor v cs is applied to an internal current measuremen t unit, and its output voltage v 1 is compared with the regulation voltage v fb . once the voltage v 1 exceeds the voltage v fb , the output flip-flop is reset. as a result, the main power switch is switched off. the relationship between the v 1 and the v cs is described by: [4] to avoid mistriggering caused by the voltage spike across th e shunt resistor at the turn on of the main power switch, a leading edge blanking time, t leb , is applied to the output of the comparator. in other words, once the gate drive is turned on, the minimum on time of the gate drive is the leading edge blanking time. in addition, there is a maximum on time, t onmax , limitation implemented in the ic. once the gate drive has been in high state longer than the maximum on time, it will be turned off to prevent the switching frequency from going too low because of long on time. 3.4 current limitation there is a cycle by cycle curren t limitation realized by the current limit comparator to provide an overcurrent detection. the source current of the mosfet is sensed via a sense resistor r cs . by means of r cs the source current is transformed to a sense voltage v cs which is fed into the pin cs. if the voltage v cs exceeds an internal voltage limit, adjusted according to the mains voltage, the comparator immediately turns off the gate drive. to prevent the current limitation process from distortions caus ed by leading edge spikes, a leading edge blanking time (t leb ) is integrated in the current sensing path. a further comparator is impl em ented to detect dangerous current levels (v cssw ) which could occur if one or more transformer windings are shorted or if the secondary diode is shorted. to avoid an accidental latch off, a spike blanking time of t cssw is integrated in the output path of the comparator. 3.4.1 foldback point correction when the main bus voltage increases, the switch on time bec omes shorter and therefore the operating frequency is also increased. as a result, for a constant primary current limit, the maximum possible output power is increased which is beyond the converter design limit. to avoid such a situation, the internal foldback point c orrection circuit varies the v cs voltage limit according to the bus voltage. this means the v cs will be decreased when the bus voltage increases. to keep a constant maximum input power of the convert er, the required maximum v cs versus various input bus voltage can be calculated, which is shown in figure 6. 0.6 0.7 0.8 0.9 1 80 100 120 140 160 180 200 220 240 260 280 300 320 340 360 380 400 vin(v) vcs-max(v) figure 6 variation of the vcs limit voltage according to th e i zc current according to the typical app l ication circuit, when mosfet is turned on, a negative voltage proportional to bus voltage will be coupled to auxiliary winding. inside coolset ? - q1 , an internal circuit will clamp the voltage on zc pin to nearly w td c zc r zc1 r zc2 ? r zc1 r zc2 + -------------------------------- - ? = v 1 3.3 v cs ? 0.7+ =
coolset ? - q1 ICE2QR0665G functional description version 2.0 10 july 4, 2011 0v. as a result, the current flowing out from zc pin can be calculated as [5] when this current is higher than i zc_1 , the amount of current exceeding this threshold is used to generate an offset to decrease the maximum limit on v cs . since the ideal curve shown in figure 6 is a nonlinear one, a digital block in coolset ? - q1 is implemented to get a better control of maximum output power. additiona l advantage to use digital circuit is the production tolerance is smaller compared to analog solutions. the typical maximum limit on v cs versus the zc current is shown in figure 7 . 0.6 0.7 0.8 0.9 1 300 500 700 900 1100 1300 1500 1700 1900 2100 iz c(ua) vcs-max(v) figure 7v cs-max versus i zc 3.5 active burst mode operation at light load condition, the ic enters active burst mode operation to minimize the power consumption. details about active burst mode operation ar e explained in the following paragraphs. 3.5.1 entering active burst mode operation for determination of entering active burst mode operation, th ree conditions apply: ? the feedback voltage is lower than the threshold of v fbeb (1.25v). accordingly, the peak current sense voltage across the shunt resistor is 0.17v; ? the up/down counter is 7; and ? a certain blanking time (t beb ). once all of these conditions are fulfilled, the active burst mo de flip-flop is set and the controller enters active burst mode operation. this multi-condition determination for entering active burst mo de operation prevents mistriggering of entering ac tive burst mode operation, so that the controller enters active burst mode operation only when the output power is really low during the preset blanking time. 3.5.2 during active burst mode operation after entering the active burst mode the feedback voltage rise s as v out starts to decrease due to the inactive pwm section. one comparator observes the feedback signal if the voltage level v bh (3.6v) is exceeded. in that case the internal circuit is again activated by the internal bias to start with switching. turn-on of the power mosfet is triggered by the timer. the p wm generator for acti ve burst mode operation composes of a timer with a fixed frequency of 52khz, typically, and an analog comparat or. turn-off is resulted by comparison of the voltage signal v 1 with an internal threshold, by which the voltage across the shunt resistor v csb is 0.34v, accordingly. a turn-off can also be triggered by the maximal duty ratio controller which sets the maximal duty ratio to 50%. in operation, the output flip-flop will be reset by one of these signals which comes first. if the output load is still low, the feedback signal decreases a s the pwm section is operating. when feedback signal reaches the low threshold v bl (3.0v), the internal bias is reset again and the pwm section is disabled until the next regulation signal increases beyond the v bh threshold. in active burst mode, the feedback signal is changing like a saw tooth between 3.0v and 3.6v shown in figure 8. 3.5.3 leaving active burst mode operation the feedback voltage immediately increases if there is a high load jum p. this is observed by one comparator. as the current limit is 34% during active burst mode a certain load is needed so that feedback voltage can exceed v lb (4.5v). after leaving active burst mode, maximum current can now be provided to stabilize v o . in addition, the up/down counter will be set to 1 iimmediately after leaving active burst i zc v bus n a r zc1 n p ------------------------ =
coolset ? - q1 ICE2QR0665G functional description version 2.0 11 july 4, 2011 mode. this is helpful to decrease the output voltage undershoot. v fbeb v fbbon v fblb v fb t v csb 1.0v v cs v vccoff v vcc t t v o t v fbboff time to 7 th zero and blanking window (t beb ) current limit level during active burst mode leaving active burst mode entering active burst mode max. ripple < 1% figure 8 signals in active burst mode 3.6 protection functions the ic provides full protection functions. the following table summarizes thes e protection functions. table 2 vcc overvoltage auto restart mode vcc undervoltage auto restart mode overload/open loop auto restart mode over temperature auto restart mode output overvoltage latched off mode short winding latched off mode protection features during operation, the vcc voltage is continuously m onitored. in case of an under- or an over-voltage, the ic is reset and the main power switch is then kept off. after the vcc voltage falls below the threshold v vccoff , the startup cell is activated. the vcc capacitor is then charged up. once the voltage exceeds the threshold v vccon , the ic begins to operate with a new soft-start. in case of open control loo p or output over load , the feedback volt age will be pulled up. after a blanking time of 24ms, the ic enters auto-restart mode. th e blanking time here enables the converter to provide a max. power in case the increase in v fb is due to a sudden load increase. during off-time of the power switch, the voltage at the zero-crossing pin is monitored for output over-voltage detection. if the voltage is higher than the preset threshold v zcovp , the ic is latched off after the preset blanking time. this latch off mode can only be reset if the vcc <6.23v. if the junction temperature of ic exceeds 140 c, the ic en ters into autorestart mode (otp). if the voltage at the current sensing pin is higher than the pres et threshold v cssw during on-time of the power switch, the ic is latched off. this is short-winding protection. during latch-off protection mo de, the v cc voltage drops to 10.5v and then the startup cell is activated. the vcc voltage is then charged to 18v. the startup cell is shut down again. this action repeats again and again. there is also a maximum on time limitation implemented ins ide the ICE2QR0665G. once the gate voltage is high and longer than t onmax , the switch is turned off immediately.
coolset ? - q1 ICE2QR0665G electrical ch aracteristics version 2.0 12 july 4, 2011 4 electrical characteristics note: all voltages are measured with respect to ground (pin 12). the voltage levels are valid if other ratings are not violated. 4.1 absolute maximum ratings parameter symbol limit values unit remarks min. max. drain source voltage v ds - 650 v t j =110 c switching drain current, pulse width t p limited by t jmax i s - 9.95 a pulse drain current, pulse width t p limited by t jmax i d_puls - 15.75 a avalanche energy, repetitive t ar limited by max. t j =150c 1) 1) repetitive avalanche causes additional power losses that can be calculated as p av = e ar *f e ar - 0.47 mj avalanche current, repetitive t ar limited by max. t j =150c i ar - 2.5 a vcc supply voltage v vcc -0.3 27 v fb voltage v fb -0.3 5.5 v zc voltage v zc -0.3 5.5 v cs voltage v cs -0.3 5.5 v maximum current out from zc pin i zcmax 3 - ma junction temperature t j -40 150 c controller & coolmos ? storage temperature t s -55 150 c thermal resistance junction -ambient r thja - 110 k/w esd capability (incl. drain pin) v esd - 2 kv human body model 2) 2) according to eia/jesd22-a114-b (discharging a 100pf capacitor through a 1.5k : series resistor) note: absolute maximum ratings are defined as ratings, whic h when being exceeded may lead to destruction of the integrated circuit. for the same reason make sure, that any capacitor that will be connected to pin 11 ( vc c ) is discharged before assembling the application circuit.t a =25 c unless otherwise specified. 4.2 operating range note: within the operating range the ic operates as described in the functional description. parameter symbol limit values unit remarks min. max. vcc supply voltage v vcc v vccoff v vccovp v
coolset ? - q1 ICE2QR0665G electrical ch aracteristics version 2.0 13 july 4, 2011 4.3 characteristics 4.3.1 supply section note: the electrical characteristics in vo lve the spread of values within th e specified supply voltage and junction temperature range t j from ? 25 c to 125 c. typical values represent the median values, which are related to 25c. if not otherwise stated, a supply voltage of v cc = 18 v is assumed. parameter symbol limit values unit test condition min. typ. max. start up current i vccstart - 300 550 ma v vcc =v vccon -0.2v vcc charge current i vcccharge1 - 5.0 - ma v vcc = 0v i vcccharge2 0.8 - - ma v vcc = 1v i vcccharge3 - 1 - ma v vcc =v vccon -0.2v maximum input current of startup cell and coolmos ? i drainin - - 2 ma v vcc =v vccon -0.2v leakage current of startup cell and coolmos ? i drainleak - 0.2 50 ma v drain = 610v at t j =100c supply current in normal operation i vccnm - 1.5 2.3 ma output low supply current in auto restart mode with inactive gate i vccar - 300 - ma i fb = 0a supply current in latch-off mode i vcclatch - 300 - ma supply current in burst mode with in active gate i vccburst - 500 950 ma v fb = 2.5v, exclude the current flowing out from fb pin vcc turn-on threshold v vccon 17.0 18.0 19.0 v vcc turn-off threshold v vccoff 9.8 10.5 11.2 v vcc turn-on/off hysteresis v vcchys - 7.5 - v 4.3.2 internal voltage reference parameter symbol limit values unit test condition min. typ. max. internal reference voltage v ref 4.80 5.00 5.20 v measured at pin fb i fb =0 junction temperature of controller t jcon -25 130 c max. value is limited by over temp erature protection of the controller junction temperature of c oolmos ? t jcoolmos -25 150 c
coolset ? - q1 ICE2QR0665G electrical ch aracteristics version 2.0 14 july 4, 2011 4.3.3 pwm section parameter symbol limit values unit test condition min. typ. max. feedback pull-up resistor r fb 14 23 33 k: pwm-op gain g pwm 3.18 3.3 - - offset for voltage ramp v pwm 0.6 0.7 - v maximum on time in normal operatio n t onmax 22 30 41 ms 4.3.4 current sense parameter symbol limit values unit test condition min. typ. max. peak current limitation in normal operatio n v csth 0.97 1.03 1.09 v leading edge blanking time t leb 200 330 460 ns peak current limitation in active bu rst mode v csb 0.29 0.34 0.39 v 4.3.5 soft start parameter symbol limit values unit test condition min. typ. max. soft-start time t ss 8.5 12 - ms soft-start time step t ss_s 1) 1) the parameter is not subjected to production test - verified by design/characterization - 3 - ms internal regulation voltage at first st ep v ss1 1) - 1.76 - v internal regulation voltage step at soft start v ss_s 1) - 0.56 - v 4.3.6 foldback point correction parameter symbol limit values unit test condition min. typ. max. zc current first step threshold i zc_fs 0.350 0.5 0.621 ma zc current last step threshold i zc_ls 1.3 1.7 2.2 ma cs threshold minimum v csmf - 0.66 - v i zc =2.2ma, v fb =3.8v
coolset ? - q1 ICE2QR0665G electrical ch aracteristics version 2.0 15 july 4, 2011 4.3.7 digital zero crossing parameter symbol limit values unit test condition min. typ. max. zero crossing threshold voltage v zcct 50 100 170 mv ringing suppression threshold v zcrs - 0.7 - v minimum ringing suppression time t zcrs1 1.62 2.5 4.5 p s v zc > v zcrs maximum ringing suppression time t zcrs2 - 25 - p s v zc < v zcrs threshold to set up/down counter to one v fbr1 - 3.9 - v threshold for downward counting at l ow line v fbzhl - 3.2 - v threshold for upward counting at lo w line v fbzll - 2.5 - v threshold for downward counting at hi g line v fbzhh - 2.9 - v threshold for upward counting at hi ghline v fbzlh - 2.3 - v zc current for ic switch threshold to high line i zcsh - 1.3 - ma zc current for ic switch threshold to low line i zcsl - 0.8 - ma counter time 1) 1) the parameter is not subjected to production test - verified by design/characterization t count - 48 - ms maximum restart time in normal operatio n t offmax 30 42 57.5 p s 4.3.8 active burst mode parameter symbol limit values unit test condition min. typ. max. feedback voltage for entering acti ve burst mode v fbeb - 1.25 - v minimum up/down value for entering active burst mode n zc_abm - 7 - blanking time for entering active bu rst mode t beb - 24 - ms feedback voltage for leaving acti ve burst mode v fblb - 4.5 - v feedback voltage for burst-on v fbbon - 3.6 - v feedback voltage for burst-off v fbboff - 3.0 - v
coolset ? - q1 ICE2QR0665G electrical ch aracteristics version 2.0 16 july 4, 2011 4.3.9 protection parameter symbol limit values unit test condition min. typ. max. vcc overvoltage threshold v vccovp 24.0 25.0 26.0 v over load or open loop detection th reshold for olp protection at fb pin v fbolp - 4.5 - v over load or open loop pr otection blanking time t olp_b 20 30 44 ms output overvoltage detection th reshold at the zc pin v zcovp 3.55 3.7 3.84 v blanking time for output overvol tage protection t zcovp - 100 - p s threshold for short winding prot ection v cssw 1.63 1.68 1.78 v blanking time for short-windding prot ection t cssw - 190 - ns over temperature protection 1) t jcon 130 140 150 c note: the trend of all the voltage levels in the cont r ol unit is the same rega rding the deviation except v vccovp 4.3.10 coolmos ? section parameter symbol limit values unit test condition min. typ. max. drain source breakdown voltage v (br)dss 650 - - v t j = 110c drain source on-resistance r dson - 0.65 1.37 0.75 1.58 : : t j = 25c t j =125c 1) 1) the parameter is not subjected to production test - verified by design/characterization at i d = 2.5a effective output capacitance, energy re lated c o(er) - 26 1) - pf v ds = 0v to 480v rise time t rise - 30 2) 2) measured in a typical flyb ack converter application - ns fall time t fall - 30 2) - ns fixed switching frequency in active burst mode f sb 39 52 65 khz max. duty cycle in active burst mo de d maxb - 0.5 -
coolset ? - q1 ICE2QR0665G typical coolmos ? performance characteristic version 2.0 17 july 4, 2011 5 typical coolmos ? performance characteristic 0.0001 0.001 0.01 0.1 1 10 100 1 10 100 1000 i d [a] v ds [v] safe operating area for ICE2QR0665G i d =f(v ds ) parameter : d = 0, t c = 25deg.c dc t p =100ms t p =0.1ms t p =1ms t p =10ms tp = 0.01ms figure 9 safe operating area(soa) curve for ice2qr0665 allowable power dissipation for quasi coolset in dso-16/12 package 0.0 0.2 0.4 0.6 0.8 1.0 1.2 0 20 40 60 80 100 120 140 ambient temperature, t a [deg.c] allowable power dissipation, p tot [w] igure 10 power dissipation p tot t a
540 580 620 660 700 -60 -20 20 60 100 140 180 t j [c] v br(dss) [v] coolset - q1 ce2qr0665 tpical coolos perforance caracteristic version 20 18 ul 4 2011 figure 11 drain-source breakdown voltage; v br(dss) =f(t j )
coolset ? - q1 ICE2QR0665G input power curve version 2.0 19 july 4, 2011 6 input power curve two input power curves gives typical input power versus ambient temperature are showed below; vin=85~265vac( figure 12 ) and vin=230vac( figure 13 ). the curves are derived based on a typical discontinuous mode flyback model which considers 115v maximu m secondary to primary reflected voltage (high priority). the calculation is based on no copper area as heatsink for the device. the input power already includes power loss at input comman mode choke and bridge rectifier and the coolmos ? . the device saturation current( i d_plus @t j =125 c) is also considered. to estimate the out power of the device, it is simply multiplying the input power at a particulary ambient temperature with th e estimated efficiency for the application. for example, a wide range input voltage( figure 12 ), operating temperature is 50 c, estimated efficiency is 85%,t he out put power is 38w(45w*0.85). 0 10 20 30 40 50 60 0 2535455565758595105115125 input power(85vac~265vac)[w] ambient temperature[ 0 c] input power curve of ice2qr0 665g figure 12 input power curve vin=85~265vac;pin=f(t a ) 0 10 20 30 40 50 60 70 80 90 100 0 2535455565758595105115125 input power(230vac)[w] ambient temperature[ 0 c] input power curve of ice2qr0 665g figure 13 input power curve vin=230vac;pin=f(t a )
coolset ? - q1 ICE2QR0665G outline dimension version 2.0 20 july 4, 2011 7 outline dimension pg-dso-16/12 (plastic dual small outline) figure 14 pg-dso-16/12 (pb-free lead plating plas tic dual small outline package) dimensions in mm
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